Method and device for detecting aircraft radio signals transmitted in the same channel simultaneously

ABSTRACT

A method for detecting at least two amplitude-modulated transmitted signals contained in a received signal within the same frequency channel with respectively different frequency displacement determines from the received signal a modified received signal by means of a nonlinear signal processing. Following this, the spectrum of the modified received signal is determined by means of Fourier transform, and at least two transmitted signals contained in the received signal are detected if at least two first spectral lines each associated with carrier signals are significantly distinguishable within the determined spectrum from spectral components associated with noise signals and payload signals.

The invention relates to a device for protecting a high-frequencyterminal from overvoltage.

High-frequency terminals are protected from overvoltages, such as canoccur, for example, as a result of lightning, by providing all inputsand outputs of an amplifier with protection elements. In EP 1 333 454A1, a coil comprising an electrically conductive wire is used for thispurpose. A coarse protection is explained in conjunction with a fineprotection. This is achieved in that the coil provides a part taperingin the direction towards an end of the coil connected to thehigh-frequency terminal.

The disadvantage with the coil from EP 1 333 454 A1 is that it must bemanufactured using a complex method, because wire must be wound onto atemplate. The template comprises a cylinder and a pin, which is attachedto a head end of the cylinder. This is costly since only small or mediumproduction runs can generally be manufactured because an electricallyconductive wire must be wound onto the cylinder and the pin in acomplicated, special manufacturing process.

The object of the invention is therefore to provide an overvoltagedevice which can be manufactured in a cost-favourable manner andrealised as far as possible with standard components.

The object is achieved by the overvoltage device according to theinvention as specified in claim 1. Advantageous further developments ofthe overvoltage-protection device according to the invention arespecified in the dependent claims.

A coil arrangement according to the invention, which is made up from twoor more separate coils in the signal path from the high-frequencyterminal to the ground potential with different, increasing inductances,is used in order to protect a circuit, for example, an amplifier, fromovervoltages which could damage the components of the amplifier, forexample, during a lightning strike. The coils in the signal path areelectrically connected in series.

The increasing inductances are preferably realised in that thecross-sections of the individual coils directly adjacent to one anotheror directly contacted with one another in the signal path increase butremain constant within one coil, so that the cross-sectional areas ofthe coils with the relatively lower inductance is accordingly smallerthan or equal to the cross-sectional areas of the directly contacted ordirectly adjacent coils with a relatively larger inductance.

As a result of the different cross-sectional areas of the coils, theresonant frequency of the coil with the relatively smallercross-sectional area is increased because of the associated reduction ofthe parasitic capacitances of the coil. The operating range of theovervoltage-protection device provided in this manner is extended in thedirection towards higher frequencies by comparison with a single coilwith constant inductance or cross-sectional area. As a result of thecoil with a relatively larger inductance or respectively cross-sectionalarea, a sufficiently high inductance is secured even for lowfrequencies, and accordingly, the blind resistance of the coil isdisposed significantly above the rated impedance of the high-frequencyterminal (generally 50 ohms). As a result of the high inductance of thecoil achieved in this manner, the overall structural length of the coilcan be kept small, so that installation within restricted spatialdimensions is also possible. Improved properties are achieved withregard to the individual resonant frequencies by comparison with theconical end disclosed in EP 1 333 454 A1.

Advantageous further developments of the overvoltage device according tothe invention can be achieved with the measures specified in thedependent claims.

Exemplary embodiments of the overvoltage-protection device according tothe invention are presented by way of example in the drawings andexplained in greater detail with reference to the following description.The drawings show:

FIG. 1 the prior art with one coil which tapers in a conical manner atone end;

FIG. 2 a plan view of a first exemplary embodiment of anovervoltage-protection device according to the invention with a coilarrangement which is made from two separate coils;

FIG. 3 a cross-section of the first exemplary embodiment according tothe invention with a coil arrangement which is made from two coils;

FIG. 4 a cross-section of a second exemplary embodiment according to theinvention with a coil arrangement which comprises two coils which areconnected to a solder pad; and

FIG. 5 a plan view of a third exemplary embodiment according to theinvention with a coil arrangement which is made from two separate coilswhich are largely magnetically decoupled;

FIG. 6 a manufacturing method for a fourth exemplary embodimentaccording to the invention made from a metal sheet;

FIG. 7A a coil winding made from a metal sheet of the fourth exemplaryembodiment with an arrangement of the metal strip in the longitudinaldirection and

FIG. 7B a coil winding made from a metal sheet of the fourth exemplaryembodiment with an arrangement of the metal strip in the radialdirection.

Parts which correspond with one another are shown with the samereference numbers in all of the drawings. In particular, the referencenumbers in FIG. 1, which relate to the prior art, are shown in agreementwith the exemplary embodiments according to the invention.

FIG. 1 shows, as the prior art, an overvoltage-protection device forprotecting a high-frequency terminal 22 from overvoltage. Thehigh-frequency terminal 22 comprises a through-connected contact 23 andan electromagnetic shield 24. The actual conduction of the signal takesplace through the contact 23, which is connected through the interior ofthe housing 21 and is referred to there as the through-connected contact23′. The coil 1 a is wound from an electric wire. The second connectingelement 5 of the coil 1 a is contacted to a ground potential 28. In thedirection of a coil axis, the coil 1 a provides a part 3 tapering in thedirection towards an end of the coil connected to the through-connectedcontact 23′ of the high-frequency terminal 22. The tapering ends at thefirst connecting element 4, which is connected to the through-connectedcontact 23′ of the high-frequency terminal 22 of a circuit 20 via asoldered connection 30. The components 26 of the circuit 20 arecontacted via a high-frequency conductor 27. The overvoltage-protectiondevice is electromagnetically insulated via a metallic housing 21 and adividing wall 21.1.

By contrast, in the exemplary embodiment shown in FIG. 2, theovervoltage-protection device according to the invention for protectinga high-frequency terminal 22 from overvoltage provides a coilarrangement 1 which comprises two or more cylindrical coils in serieswith n different, cross-sectional areas A₁, A₂, . . . , A_(n) increasingin size, or respectively, in the case of circular cross-sections, withincreasing diameters d₁, d₂, . . . , d_(n). In this context, n denotesthe number of coils. The coil end with the smallest cross-sectional areaA₁ is connected to the high-frequency terminal 22 shown in FIG. 3 via afirst connecting element 4. A second connecting element 5 for the coilend with the largest cross-sectional area A_(n) is connected eitherdirectly or via a current source or voltage source 11 to a groundpotential 28. In general, this is a direct voltage (DC) source.

FIG. 2 shows the plan view of the first exemplary embodiment of a deviceaccording to the invention for protecting the circuit 20. The structureaccording to the invention is surrounded by a metallic housing 21. Thisprovides electromagnetic shielding. The coil arrangement 1 guides thethrough-connected contact 23′of the high-frequency terminal 22 to thecurrent or voltage supply 11. The circuit 20 to be protected or thecomponents 26 to be protected are contacted both to the high-frequencyterminal 22 and also to ground potential 28. The printed-circuit board25 is metallised over its full area. Only a rectangular cut-out 10 inthe metallisation 16 is provided under the coil arrangement 1 orrespectively under each of the coils L₁, L₂, . . . , L_(n).

FIG. 3 illustrates a cross-section through the exemplary embodiment ofthe overvoltage-protection device already explained in FIG. 2. Thehigh-frequency terminal 22 is additionally shown. This is guided to thecircuit 20 from above. The circuit 20, the coil arrangement 1 and thecurrent or voltage source 11 are disposed on the printed-circuit board25, which is attached to the housing 21 with support elements 15. Acut-out 12 in the metallic housing 21, which can be manufactured, forexample, by milling or with an appropriately shaped die, is disposeddirectly under the coil arrangement 1. The additional hollow cavity orspacing of the cut-out 12 saves weight and achieves a considerablereduction of parasitic capacitances. The two coils L₁, L₂, which formthe coil arrangement 1 are electromechanically connected to one anotherby a length of wire 14.

The coil arrangement 1 is advantageously made up from a first coil L₁and a second coil L₂, comprising separate coils, which areelectromechanically connected to one another, especially by a solderedconnection. The ends of the individual coils L₁, L₂ are preferablyembodied as contact points and can be connected to one another. However,other connections, such as plug connections, welding, twisting orbiscuit connectors are also conceivable. The same applies for thefurther coils L₁, L₂, . . . , L_(n) electromechanically contacted ordirectly connected to one another. In this manner, standard componentscan be used for the manufacture of the coils 1, so that the costlyprocess of winding a wire onto a template can be dispensed withaccording to the invention.

The exemplary embodiment illustrated in FIG. 4 differs from FIG. 3 inthat the connection of the two coils L1, L2 is not provided through aconnection with a simple length of wire, but the projecting legs 19 ofthe coils L₁, L₂ are attached to a solder pad 18 preferably by reflowsoldering, that is, the electromechanical connection of the separatecoils L₁, L₂, . . . , L_(n) is achieved with solder pads 18 which arecontacted with legs 19 of the coils L₁, L₂, . . . , L_(n). On its rearside, the solder pad 18 also provides a metallisation 17 which iscontacted to the ground potential 28.

The ends of the individual coils L₁, L₂ are preferably embodied ascontact points and can therefore simply be electromechanically connectedto a solder pad 18 or a printed circuit board 25. The legs 19 can beoptimised for reflow soldering. For example, the shape of the legs 20can be adapted by means of pressing tools. Accordingly, the coil 1according to the invention can be manufactured simply, rapidly and in acost favourable manner in medium to large production runs.

In a further embodiment, the leads h between the individual coilportions differ, so that both the inductance and also the capacitance ofthe individual coil portions vary. In particular, the inductance L isvaried in that, in equation 1, the number of windings N progresses in aquadratic manner, while the lead h between the individual windings inequation 2, determines the capacitance C in a reciprocal manner. A isthe cross-sectional area, μ is the permeability and ε is the dielectricconstant

L=μ*N ²/1*A   (1)

C=ε*A/h   (2)

The frequency range which can be covered by the coil arrangement 1 canbe further increased in that the wire diameter of the second coil L₂ islarger than the wire diameter of the first coil L₁, or respectively, inthat the wire diameter increases or at least remains constant with anincreasing cross-sectional area A₁, A₂, . . . , A_(n) or inductance ofthe individual coils L₁, L₂, . . . , L_(n), so that the wire diameter ofthe coils L₁, L₂, . . . , L_(n) with relatively lower inductance issmaller than or equal to the wire diameter of the coil with therelatively larger inductance L₁, L₂, . . . , L_(n) directly electricallycontacted or directly adjacent to the named coil L₁, L₂, . . . , L_(n).

This has the advantage that the capacitance between the individualwindings in the signal path from the high-frequency terminal 22 to theground potential 28 of the observed coil L_(k) is smaller than thecapacitance between the windings of the directly following coil L_(k+1)in each case. In this context, k is a natural number with values from 1to n−1. As a result of the associated, relatively lower parasiticcapacitance of the observed front coil L_(k), the resonant frequency isincreased, so that the operating range of the overvoltage-protectiondevice is accordingly additionally extended towards relatively higherfrequencies. This effect cannot be achieved in technical production witha single conical coil, because this would then necessitate differentwire thicknesses along its length, so that it could be wound onto atemplate.

The electrically conductive wire preferably comprises lacquered copperwire with a cross-sectional area of 0.1-1 mm². The cross-sectional areaof the wire determines the maximum current, which can be drained, forexample, in the event of a lightning strike. In one advantageousembodiment, the individual windings of the coil arrangement 1 are woundtightly together.

In a further embodiment of the invention, as shown in FIG. 6, coils canbe manufactured by separating extremely elongated rectangles 6 of length1, width b and thickness h from a thin sheet 7 preferably made of metal,for example, by cutting, especially with a laser, or by punching.

In an embodiment illustrated in FIG. 7A, coils L₁, L₂, . . . , L_(n) oflow capacitance, that is, with a high resonant frequency, are wound insuch a manner that the thickness d determines the capacitance betweenthe individual windings of the coils L₁, L₂, . . . , L_(n). Bypreference, the coils L₁, L₂, . . . , L_(n) of this design of theperpendicular type 31, as illustrated in FIG. 7A, also provide a smallcross-sectional area A₁, A₂, . . . , A_(n). With this design, therelatively narrower surfaces, which correspond to the thickness of themetal sheet and are not illustrated in FIG. 7A and FIG. 7B, are disposedopposite to one another.

In a further design illustrated in FIG. 7B of the flat type 32, coilsL₁, L₂, . . . , L_(n) with a high capacitance with an approximatelyidentical inductance by comparison with FIG. 7A, that is, of lowresonant frequency, are wound in such a manner that the width bdetermines the capacitance between the individual windings of the coilsL₁, L₂, . . . , L_(n). With the shape of the coil of the flat type 32,the relatively larger surfaces are disposed opposite to one another. Inthis manner, the maximum possible current in all coils L₁, L₂, . . . ,L_(n) of the coil arrangement 1 can be of the same magnitude, but afurther degree of freedom is obtained for adjusting the inductance orrespectively the capacitance of the individual coils L₁, L₂, . . . ,L_(n). In particular, the resonant frequency can be reduced, if thecapacitance between the windings of a coil L₁, L₂, . . . , L_(n) isincreased by positioning the flat sides of the windings with a smallspacing distance from one another.

If the flat sides are positioned facing radially outwards, that is, sothat the normal of the flat side faces radially outwards, ideally with alarge spacing distance from the coil windings, a very high resonantfrequency is obtained, because the coils L₁, L₂, . . . , L_(n) providesa low capacitance and inductance.

FIG. 6 and FIGS. 7A and 7B are not shown to scale for reasons ofimproved visual orientation. However, the ratio 1>>b>3h applies, and thecross-sectional area of the current-conducting, metallic strip 6 woundinto a coil L₁, L₂, . . . , L_(n) should be constant in the case ofcoils L₁, L₂, . . . , L_(n) in a coil arrangement 1.

It is advantageous that the ratio of the inductances of the first coilL₁ relative to the second coil L₂ or respectively two coils L₁, L₂directly electrically contacted or directly adjacent to one another isdisposed between 4 to 1 and 16 to 1, preferably at approximately 8 to 1.The diameters of the second and the first coil L₂, L₁ provide a ratiobetween 1.5 to 1 and 3 to 1, particularly advantageously a ratio from 2to 1. Typical diameters of the first round coil L₁ are disposed between1 mm and 4 mm, especially 2 mm. Typical diameters of the second roundcoil L₂ are disposed between 1 mm and 4 mm, especially 2 mm. Thediameter of the first coil L₁ should advantageously be smaller than thediameter of the second coil L₂.

Further possible embodiments are formed by coils with rectangular oroval cross-section instead of circular.

The corresponding cross-sectional areas A₁, A₂ for round coils can bedetermined with reference to equation 3, in which A denotes thecross-sectional area and d denotes the diameter.

A=π*(d/2)̂2   (3)

Accordingly, a corresponding cross-sectional area A₁ of the first coilL₁ between 0.78 mm² and 12.57 mm², especially 3.14 mm² is obtained. Thecorresponding cross-sectional area A₂ of the second coil L₂ is between3.14 mm² and 28.27 mm², especially 12.56 mm². In general, the lengths ofthe individual coils with different diameter or respectively differentcross-sectional area are approximately identical.

The overvoltage device is conventionally disposed on a printed circuitboard 25 metallised over its entire surface, which is contacted toground potential 28. Parasitic capacitances between the coils L₁, L₂, .. . , L_(n) and the printed-circuit board 25 can be significantlyreduced through cut-outs 10 in the metallisation 16 of the printedcircuit board 25, especially rectangular cut-outs under the coils L₁,L₂, . . . , L_(n).

According to the invention, the coil arrangement 1 is preferablyimplemented as an air coil. An air coil provides the advantage of a lowmass. However, especially in the case of different leads h, it isadvantageous to provide coil portions with a soft-magnetic core, so thateach coil portion L₁, L₂, . . . , L_(n) can be optimised individually,without influencing the other coil portions L₁, L₂, . . . , L_(n) viastray fields or influencing the coil portion L₁, L₂, . . . , L_(n). Itmay also be advantageous to provide only certain coil portions L₁, L₂, .. . , L_(n) with a magnetic core.

As an alternative, in a further embodiment, a decoupling of theindividual coil portions L₁, L₂, . . . , L_(n) can be largely achieved,as shown in FIG. 5, in that the directly, electromechanically contactedor adjacent coil portions are orientated in different directionsrelative to one another, preferably orthogonally. Accordingly, themagnetic fields of the individual coil portions L₁, L₂, . . . , L_(n)hardly influence one another. However, coil portions L₁, L₂, . . . ,L_(n) not directly adjacent or not directly contacted can also bearranged with a parallel orientation, provided the coil portions L₁, L₂,. . . , L_(n) are disposed with an adequate geometric spacing distancefrom one another, for example, approximately 5 mm. The cut-outs 10 inthe metallisation 16 under the individual coils L₁, L₂, . . . , L_(n)are advantageously rectangular and can overlap as illustrated in FIG. 5.

A further alternative for the electromagnetic decoupling of the coilsL₁, L₂, . . . , L_(n) is to attach, in each case between the individual,especially the directly electrically contacted or mutually, directlyadjacent coils L₁, L₂, . . . , L_(n), a metallic, ideallynon-magnetisable, electrically conductive plate 9, which is electricallyconnected to ground potential 28, as illustrated in FIG. 2. The plate 9can be attached with support elements 15 to the printed circuit board 25or to the housing 21.

It is also advantageous, if the outer regions of the coil arrangement 1are distanced, for example, by at least 3 mm from the housing 21 and/orfrom electrically conductive parts. This significantly reduces theinfluence of parasitic capacitances. The housing 21 is generally alsoconnected to ground potential 28. However, in order to occupy as littlevolume as possible, the spacing distance should not be greater than 10mm. A spacing distance of, for example, approximately 5 mm is thereforeselected by preference.

According to the invention, all of the devices described can also berealised with more than two coils and combined with one another. All ofthe features described or illustrated can be combined with one anotheras required within the scope of the invention.

1. A method for detecting at least two transmitted signals contained ina received signal within a same frequency channel with respectivelydifferent frequency displacement, comprising: determining a modifiedreceived signal by using nonlinear signal processing of the receivedsignal; determining a spectrum of the modified received signal by usinga Fourier transform; and detecting at least two transmitted signalscontained in the received signal if at least two first spectral lineseach associated with carrier signals are distinguishable within thedetermined spectrum from spectral components associated with noisesignals and payload signals.
 2. The method according to claim 1, whereinat least two transmitted signals contained in the received signal aredetected if at least two first spectral lines of carrier signalscontained in the modified received signal are identified within thedetermined spectrum, of which amplitudes are respectively a multiple ofthe mean value of an amplitude of the spectral components of the noisesignals and payload signals contained in the modified received signal.3. The method according to claim 2, wherein the identified firstspectral lines of the carrier signals are direct signal components,harmonics, and/or intermodulation products.
 4. The method according toclaim 1, wherein second spectral lines of periodic signal components ofthe payload signal contained in the modified received signal positionedsymmetrically to the first spectral lines are identified and blanked outof the determined spectrum of the modified received signal.
 5. Themethod according to claim 4, wherein two second spectral linespositioned symmetrically to a first spectral line are identified if, ineach case, two spectral lines exist for each identified first spectralline of which intervals in the frequency displacements from therespective first spectral line differ by a maximum of a first thresholdvalue.
 6. The method according to claim 4, wherein in order to identifysecond spectral lines, the spectral lines with the largest amplitudes inthe spectrum of the modified received signal are used respectively asfirst spectral lines.
 7. The method according to claim 4, wherein, inorder to increase frequency resolution in determining intervals in thefrequency displacements, an FFT length of the Fourier transform isincreased.
 8. The method according to claim 2, wherein at least twotransmitted signals contained in the received signal are detected if,after blanking out second spectral lines, at least three first spectrallines are identified in the spectrum of the modified received signal, ofwhich the amplitudes are respectively a multiple of the mean value of anamplitude of spectral components of non-periodic signal componentscontained in the modified received signal.
 9. The method according toclaim 8, wherein at least two transmitted signals are detected in themodified received signal if, after blanking out second spectral lines,at least three spectral lines is disposed in the spectrum of themodified received signal, of which the amplitudes are higher than asignificance level such that a second threshold value above the meanvalue of the amplitudes of the spectral components of the non-periodicsignal components contained in the modified received signal.
 10. Themethod according to claim 8, wherein at least two transmitted signalsare detected in the modified received signal if, after blanking outsecond spectral lines, at least three spectral lines are disposed in thespectrum of the modified received signal, which are selected by using acyclostationary property detection of the non-periodic signal componentsin the modified received signal.
 11. The method according to claim 8,wherein at least two further transmitted signals are detected in themodified received signal if, after blanking out second spectral lines,at least three spectral lines are disposed in the spectrum of themodified received signal, which are selected by using a Jarque-Bera testof the non-periodic signal components in the modified received signal.12. The method according to claim 1, wherein the nonlinear signalprocessing is a quadratic signal processing.
 13. The method according toclaim 2, wherein, for the identification of first and second spectrallines, the spectrum of the modified received signal is analysed in afrequency range of a second harmonic of the transmitted signalscontained in the modified received signal.
 14. The method according toclaim 1, wherein the nonlinear signal processing is a modulus function.15. The method according to claim 14, wherein, for the identification offirst and second spectral lines, the spectrum of the modified receivedsignal is analysed in a frequency range surrounding a direct signalcomponent of the modified received signal.
 16. A device for detecting atleast two transmitted signals contained in a received signal withdifferent frequency displacement, comprising: a nonlinear signalprocessing unit for determining a modified received signal throughnonlinear signal processing of the received signal; a Fouriertransformer for determining a spectrum of the modified received signal;and a detector for identifying multiple first spectral lines associatedrespectively with carrier signals, which are distinguishable fromspectral components associated with noise signals and payload signals.17. The device according to claim 16, further comprising a unit providedfor blanking out from the spectrum of the modified received signalsecond spectral lines which are positioned symmetrically to the firstspectral lines.
 18. The device according to claim 16, further comprisinga unit provided for implementation of a significance test.
 19. Thedevice according to claim 16, further comprising a unit provided forimplementation of a cyclostationary property detection.
 20. The deviceaccording to claim 16, further comprising a unit provided forimplementation of a Jarque-Bera test.